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HT9015 rf single chip for cordless phone 1 april 10, 2000 features operating voltage: 2.7v~6v extremely low power consumption current i cc =0 a (typ.) in battery-saving mode i cc = 8.5ma (typ.) in standby mode i cc = 13.5ma (typ.) for communication built-in if decoder, compander and pll if decoder 1st/2nd mixers, rx vco rssi quadrature detector, if amp noise detector compander expander, compressor, limiter receive amp, mic amp, pre amp pll rx pll, tx pll local oscillator data latch control unlock detector four threshold variable battery alarms general description the HT9015 is an rf single chip for cordless phone systems. internally these are three major parts, a pll, an if decoder and a compander. the pll provides radio channel selection for either the transmitter or receiver. frequency locking status of the selected channel can be monitored by a control register. the if decoder provides two frequency down converters that let high frequency signals pass through a mixer and local oscillator to be low- ered for frequency even base band signals. it also provides an rssi (receiver signal strength indicator) function to detect the if output sig- nal strength and built-in noise detector for s/n quality. the compander provides better s/n ratio for audio signal processing. the HT9015 has a wide-range applications in fm/fsk, transmitting/receiving of vhf bandwidth including cordless phone, narrow band voice and data transceiver systems. the most significant advantage of the HT9015 is in the reduction of many external compo- nents making it well suited for cordless phone baseset, handset radio section. preliminary
block diagram HT9015 2 april 10, 2000 preliminary
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pin assignment pin description pin no. pin name i/o description 1 vco2 i connects lc network with vco1 pin to provide the tank circuit for the received voltage control oscillator 2 c_rect normally connected to ground through a capacitor. 3 rx_out o receiver phase detector output. the pdt of rx-pll detects phase errors from the received pll. the output is connected to external low pass filter. 4 tx_out o transmitter phase detector output. the pdt of tx-pll detects phase errors from the transmitted pll. the output is connected to an external low pass filter. 5 gnd2 digital ground 6 tx_in i 14-bit programmable transmit counter input. the output signal from the external vco circuit can be ac coupled to this pin. HT9015 3 april 10, 2000 preliminary $ % $ % % $ % $ ! 2 !)) ( ! ! ! ! -)! ) ! ! ())

pin no. pin name i/o description 7 vcc3 positive power supply for digital block circuits. 8 lo1 i this pin connects to lo2 pin with external crystal and capacitor. 9 lo2 o this output pin generates a reference frequency used for the pll and the second mixer local oscillator when connected to lo1 pin with an external crystal and capacitor. 10 sig_out o this pin outputs four-type states and is selected by an internal control register. there are rssi state and noise state and rx/tx pll lock states. open drain output. 11 clk i clock input pin 12 data i serial data input pin 13 stb i data strobe control pin 14 fil_out o splatter filter output pin 15 fil_in i splatter filter input pin 16 comp_out o compressor output pin 17 c_nf normally connected to ground through a capacitor. 18 mic_out o microphone amplifier output pin 19 mic_in i microphone amplifier input pin 20 pre_in i pre-amplifier input pin 21 pre_out o pre-amplifier output pin 22 exp_out o expander output pin 23 rece_in i receiver amplifier input pin 24 ro1 o receiver amplifier output pin 25 ro2 o receiver amplifier output pin 26 bat_alm o battery alarm output pin. when the battery voltage is lower than the internal setting threshold this pin is active. open drain output. 27 rssi o receiver signal strength indicator output pin, the output signal depends on the if amplifier output signal. 28 d_comp_out o data comparator output pin 29 d_comp_in i data comparator input pin. input to comparator to distinguish digital data from audio. 30 n_fil_in i input to noise filter 31 n_fil_out o output from noise filter HT9015 4 april 10, 2000 preliminary
pin no. pin name i/o description 32 af_out o fm demodulator output pin. output signal frequency is within the audio band. 33 quad i normally provides a 455khz carry frequency for the fm quadra - ture detector. 34 if_out o if amplifier output pin. signal will later pass through external 90 c phase shifter for quadrature detector. 35 gnd1 analog ground 36 dec normally connected to vcc1 through a capacitor. 37 if_in i if amplifier input pin it is necessary to use the if filter network to get high quality if signal. 38 vcc1 analog power supply 39 2ndmix_out o second mixer if signal output pin and down converter. if fre - quency is 455khz. 40 n_rec connect to ground through capacitor. 41 2ndmix_in i second mixer rf signal input pin and down converter. fre - quency is 455khz. 42 e_rect expander rectifier filter capacitor pin. 43 1stmix_out o first mixer if signal output pin and down converter. if fre - quency is 10.7mhz. 44 vref o reference voltage input for compander. 45 1stmix_in i the first mixer rf signal input. carrier frequency from 20~60mhz. 46 vcc2 directly connects to the two voltage regulators inside. 47 vco_cont i normally connected to ground through a capacitor. 48 vco1 i connects lc network with vco2 pin to provide the tank circuit for the received voltage control oscillator. absolute maximum ratings supply voltage...........................v ss 0.3v to 6v storage temperature................. 55 cto150 c input voltage .................v ss 0.3v to v cc +0.3v operating temperature .............. 20 cto70 c note: these are stress ratings only. stresses exceeding the range specified under absolute maxi - mum ratings may cause substantial damage to the device. functional operation of this device at other conditions beyond those listed in the specification is not implied and prolonged expo - sure to extreme conditions may affect device reliability. HT9015 5 april 10, 2000 preliminary
electrical characteristics ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions v cc operating voltage v cc1 =v cc3 3.6 v i cc1 current 1 consumption 3.6v all on 13.5 ma i cc2 current 2 consumption 3.6v rx-rf on 8.5 ma i cc3 current 3 consumption 3.6v rx-af on 3.5 ma i cc4 current 4 consumption 3.6v tx-rf on 2.1 ma i cc5 current 5 consumption 3.6v tx-af on 1.7 ma i cc(a) current alarm supply 3.6v r l = 100k 100 a i cc(bs) supply current in battery saving mode 3.6v all off 0 a i ref v ref voltage 3.6v 1.5 v v ih data input threshold 3.6v v cc3 v v il data input threshold 3.6v 0 v i ih data input current 3.6v v ih =v cc 0 a i il data input current 3.6v v il = gnd 0 a f ck ck input frequency 3.6v 38 1000 khz regulator ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions v reg output voltage 3.6v i out = 1ma 1.7 2 2.3 v i out (min) minimum load current 3.6v v out =v reg (open) 0.05v 3 ma detector ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions v bat-l detection voltage 1 3.6v 3.3 v v bat-h detection voltage 1 3.6v 3.37 v v bat-l detection voltage 2 3.6v 3.15 v v bat-h detection voltage 2 3.6v 3.2 v HT9015 6 april 10, 2000 preliminary
symbol parameter test conditions min. typ. max. unit v cc conditions v bat-l detection voltage 3 3.6v 3.05 v v bat-h detection voltage 3 3.6v 3.10 v v bat-l detection voltage 4 3.6v 2.78 v v bat-h detection voltage 4 3.6v 2.82 v v ol output low level voltage 3.6v i sink = 0.1ma 0.1 v i leak output leak current 3.6v v alm = 3.6v 0 a v th minimum detection level 3.6v f= 500hz mvrms v ol output low level voltage 3.6v i sink = 0.2ma 0.1 v i leak output leak current 3.6v v data = 3.6v 0 a v th-h noise detection level 3.6v 0.57 v v th-l noise detection level 3.6v 0.47 v v ol noise detection level voltage 3.6v i sink = 0.2ma 0.1 v i leak output leak current 3.6v vsig= 3.6v 0 a v th-l rssi comparator detection voltage 3.6v comparator output l h 0.72 v v th-h rssi comparator detection voltage 3.6v comparator output h l 0.8 v v hys rssi comparator hysteresis 3.6v 0.08 v pll detection db v=db v emf (open), ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions f in operating frequency 3.6v 46.61 mhz v in tx-pll input sensitivity 3.6v 103 db v v lo local oscillator input sensitivity 3.6v f lo = 10.240mhz 110 db v i cp1 charge pump output current 3.6v v cp = 1.8v 200 a i cp2 charge pump output current 3.6v v cp = 1.8v 400 a i leak charge pump leak current 3.6v 0 a f lo local oscillator operating frequency 3.6v v lo = 112db v 10.24 mhz HT9015 7 april 10, 2000 preliminary
rx-vco if + mix section f in (mix 1)=46.61mhz, f in (if)=455khz, f=3khz f m = 1khz, db v=db v emf (open), ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions k v conversion gain 3.6v 1 mhz/v v vco rx vco oscillation level 3.6v f vco = 25~55mhz 110 db v 1st and 2nd mixer, if amp ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions 12db sinad 12db sinad sensitivity 3.6v input 50 20 db v f mix1 mixer operating frequency 3.6v 1stmixer 46.61 mhz f mix2 mixer operating frequency 3.6v 2ndmixer 10.7 mhz g vc conversion gain 3.6v excluding filter loss 26 db g if if amp gain 3.6v 75 db v od demodulated output 3.6v v in (mix 1)= 70db v 220 mvrms s/n s/n ratio 3.6v v in (mix 1)= 70db v 55 db amr am rejection ratio 3.6v v in (mix 1)= 70db v 40 db r in1 input impedance 3.6v 1st mix in 2.1 k c in1 input impedance 3.6v 1st mix in 3.5 pf r in2 input impedance 3.6v 2nd mix in 5.8 k c in12 input impedance 3.6v 2nd mix in 2.5 pf r in input resistance 3.6v if in 1.5 k r o1 output resistance 3.6v 1st mix out 330 r o2 output resistance 3.6v 2nd mix out 1.5 k v rssi1 rssi output voltage 3.6v v in (mix 1)= 20db v 1 v v rssi2 rssi output voltage 3.6v v in (mix 1)= 60db v 2.4 v HT9015 8 april 10, 2000 preliminary
compressor + mic amp f in =1khz, ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions v refc input reference level 3.6v v om = 10dbv 10.5 dbv v oc output deviation 3.6v v om = 30dbv 0.2 db v 4 mic amp voltage gain 3.6v 20 db t hdc total harmonic distortion 3.6v v om = 10dbv 0.3 % v noc output noise level 3.6v input-gnd short 61 dbv v lim1 limiting level 3.6v comp out, v im = 0dbv 1.3 v p-p v lim2 limiting level 3.6v mic out, v im = 0dbv 2.6 v p-p v mute mute output level 3.6v 96 dbv expander + pre amp + receiver amp ta=25 c symbol parameter test conditions min. typ. max. unit v cc conditions v refe input reference level 3.6v v op = 10dbv 10 dbv v oe output deviation 3.6v v op = 35dbv 0.5 db g p3 pre amp voltage gain 3.6v 0 db thd1 total harmonic distortion 3.6v r l = 150 v ri = 15dbv 0.5 % v mute mute output level 3.6v 76 dbv g rng2 pre amp voltage gain setting range 3.6v 0 db g rng1 receiver amp voltage gain setting range 3.6v 6 db ct ce crosstalk ce 3.6v v im = 20dbv 95 db g s voltage gain 3.6v 0 db dr s maximum output level 3.6v thd= 3% 3 v p-p HT9015 9 april 10, 2000 preliminary
HT9015 10 april 10, 2000 preliminary functional description the HT9015 is a signal chip rf ic for cordless phone applications. it has applications for 46/49mhz cordless phones as well as ct0 cord - less phones that have frequency bands between 20mhz and 60mhz. this chip enables external components in the base set and hand set radio section application circuits to be reduced. the HT9015 is manufactured or a special pro - cess called bicmos, or bipolar process and cmos process. because the rf and if parts need high frequency actions such as mixer, vco, if amplifier and demodulator, those parts are implemented in high performance bi - polar circuits. the other digital functions are designed using cmos circuits. sometimes this chip is known as combo , the meaning of combo is one chip combined with rf, if and pll parts. the HT9015 provides data latch interface con - trolled by a microcontroller. there are four in - ternal registers inside the HT9015; tx (transmitter) divider, rx (receiver) divider, ref (reference) divider and control register. all registers can be set through the data latch control interface. the data latch control inter- face contains data, clk and stb control sig- nals. input timing for serial data data is read on the timing of the rising edge of clk. when stb receives a high signal, data in the shift register is sent into the latch to con - trol the block, see the input timing for serial data as shown below. serial data format of four registers according to previous input timing specs, the HT9015 can be easily set up using four regis - ters. the tx divider determines the tx pll locked frequency; the rx divider determines the rx pll locked frequency; the ref divider determines the tx and rx pll frequency ref - erence which is also called channel space. the control register is an important unit which con - trols the radio link, voice control and power sav - ing during base set and hand set communication. all data format contains 20 bits, but some regis - ters need only 16 bits, they have a common field of 20 bits data format called code which determine what data belongs to whom. see the table below. code register 1 1 ref register 1 0 tx register 0 1 rx register 0 0 control register four register selection 3
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HT9015 11 april 10, 2000 preliminary ref register divide number range is from 5 to 4095. this register includes test bits which must be set to 0. divide number: r= r0 + r1
2 r2
2 2 +r3
2 3 + +r11
2 11 bc bit is battery alarm detection setting. tx register divide number range is from 5 to 16383. divide number: n= n0 + n1
2+n2
2 2 +n3
2 3 + + n12
2 12 + n13
2 13 rx register divide number range is from 5 to 16383. divide number: n= n0 + n1
2+n2
2 2 +n3
2 3 + + n12
2 12 + n13
2 13 control register this register includes battery saving control for the tx/rx circuits or mute controls for the com - mander block or changing threshold level for the battery alarm. $ ( &# 17
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HT9015 12 april 10, 2000 preliminary battery saving control 0 operation 1 battery saving bit control block tx-rf tx-pll tx-rf= 1 and rx-rf= 1 local osc= off tx-af mic amp, compressor, splatter rx-rf rx-vco, rx-pll, 1st mix, 2nd mix if amp, noise det, data comp, rssi rx-af pre amp, expander, receiver amp mute control 0 normal 1 mute mute for compressor output. these bits prevent the compander block going into a battery saving mode. current consumption therefore does not decrease. charge pump current control pll loop performance such as lock-up time can be changed by these control bits. bit control output 0 1 tx cp tx-pll charge pump output current 200 a 400 a rx cp rx-pll charge pump output current 200 a 400 a battery alarm detection setting there are has four threshold levels for low battery detection. these threshold levels are shown on the table below. (1) bc ba1 ba2 v bat-l 0 0 0 3.00v 0 0 1 3.25v 0 1 0 3.30v 0 1 1 3.45v 10 0 (2) battery saving 11 1 (1) bc bit in ref divider (2) only for battery alarm block
HT9015 13 april 10, 2000 preliminary sig_out selection the sig_out terminal generates combination states of rx and tx lock detectors. the rssi and noise detector are shown in figure 2 below. sw1 and sw2 in fig. 3 determine the output on sig_out using selection bits in a control regis - ter according to the figure below. ! ! 2! < ! ! ) < ! ! ! ) " "+* "+* figure 3 signal output block diagram ! ! ! ! /
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HT9015 14 april 10, 2000 preliminary example of divider setting when the local osc frequency is 10.240mhz, rx vco has to oscillate at frequencies from 35.915mhz in 20khz or 25khz step. reference frequency at the phase detector should be set to 5khz. 10.240mhz 5khz = 2048, r= 2048 calculate dividing number n for rx divider 35.915mhz 5khz = 7183, n (ch16)= 7183 35.935mhz 5khz = 7187, n (ch17)= 7187 finally you set the following registers. the power saving arrangement is one of the features in the HT9015. this is achieved through an inside control register to arrange the power consumption of the three major parts (rf. if. pll). there are two-pair dc power supplies for the HT9015, v cc1 -gnd1 and v cc3 -gnd2. the dc power v cc1 provides operating voltage for the if detector and the compander analog parts. the dc power v cc3 provides the operating voltage for the pll and data latch control. it also has a built in 2.0v regulator vcc2 for the rx front end. see the power supply arrangement as shown on the table below. vcc1 gnd1 1st mix, 2nd mix, if amp, quad, noise det. rx-vco data comp, compander, receiver amp, splatter. vcc3 gnd2 rx-pll, tx-pll, local osc, data latch control $ $ $ $ $ $ $ $ &# ( !
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HT9015 15 april 10, 2000 preliminary intermediate frequency (if) decoder part the figure below shows a simplified block dia - gram for a double-conversion super heterodyne fm receiver. heterodyne means to mix two fre - quencies together in a non linear device or to translate one frequency to another using non linear mixing. the super heterodyne receiver is an improvement over other receiver in gain, se - lectivity, and sensitivity characteristics. the super heterodyne receiver is divided into five parts: rf section. generally consists of a preselector and an amplifier stage. mixer conversion section. includes a ra - dio-frequency oscillator stage (commonly known as a local oscillator) and a mixer con - version stage (commonly known as a fre - quency detector) to produce the if signal. the if section. generally consists of a series of if amplifiers and bandpass filters and known as the if strip. most of the receiver gain and se - lectivity is achieved in the if section. the fm demodulator section: the quadrature fm demodulator uses a 90 phase shift, a sin - gle tuned circuit, and a product detector to de - modulate the fm signals. the audio amplifier section. the audio section comprises several cascaded audio amplifiers and one or more speakers. the number of am- plifiers used depends on the audio signal power desired. mixers a mixer is a non linear device whose purpose is to convert radio frequencies (rf) to inter - mediate frequency (if) (rf-to-if frequency translation). in the frequency conversion pro - cess, rf signals are combined with the local oscillator frequency in a non linear device. the output of the mixer contains an infinite number of harmonic and cross-product fre - quencies which include the sum and the dif - ference between the desired rf carrier and the local oscillator frequencies. the if band-pass filter are tuned to the different fre - quencies. therefore, the if signal is filtered out by the bpf. in the HT9015 the double con - version method (figure 4) is applied to pro - duce the lower if. the first if is a relatively high frequency (10.7mhz), for good image-frequency rejec- tion, while the second if is a relatively low frequency (455khz) that allows the if ampli- fiers to have a relatively high gain and still not be susceptible to oscillations. */& 1+, 0*
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HT9015 16 april 10, 2000 preliminary limiting if amplifier, rssi (received signal strength indicator) and rssi comparator the basic function of the if amp is to boost the if signal and to help handle impulse noise. the if limiter applies very high gain to the if frequency such that the top and bottom of the waveform are clipped. this helps in re - ducing am and noise intercepted upon recep - tion. the limiting if amplifier consists of four differential amplifiers (figure 6). quadrature detector once the signal leaves the if section, it must be demodulated so that the baseband signal can be separated from the if signal. this is accomplished by the quadrature detector. a quadrature detector (figure 7) uses a 90 phase shifter (c i ), an l/c tuned circuit, and a phase comparator to demodulate fm signals. "# ) ) ) ) ! 1 - . + # + . !/& a b " "+* 1+"> 1 figure 6 limiting if amplifier, rssi and rssi comparator !! ) ( . ??
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HT9015 17 april 10, 2000 preliminary noise detector figure 8 is a band pass filter which can detect noise energy on n_rec pin. there is also a pass through the noise comparator to deter - mine two states on sig_out pin by internal control register setting. the high state ex - presses noise level more than 0.4v and the low state expresses noise level under 0.4v. !! &

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HT9015 18 april 10, 2000 preliminary &
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., 0+"# "0. 0+"# .0. figure 9 illustration of compressed and extended signal compander the compander (compressor and expander) is composed of two variable gain circuits which provide compression and expansion of the sig - nal dynamic range. in consideration of the wide band noise and maximum dynamic range which exist in the transmission medium, the general signal handling technique lowers the general communication quality by reducing the s/n ratio and generating a clipping phenome - non. however the compander improves the communication quality by automatically con - trolling the gain based on the input signal level to increase the valid dynamic range and to im - prove the s/n ratio. in the HT9015, the compressor will take a sig - nal with a 75db dynamic range ( 5db to 80db), and reduce it to a 37.5db dynamic range ( 7.5db to 45db) by attenuating strong signals,while amplifying low level signals. the expander does the opposite in that the 37.5db signal range is increased to a dynamic range of 75db by amplifying strong signals and attenu - ating low level signals. the 0db level is inter - nally set at 316.227mvrms that is the signal level which is neither amplified nor attenuated. see figure 9 below. through the action of the compander, the noise of the transmission me - dium is constant under 80dbv.
HT9015 19 april 10, 2000 preliminary pll the figure below shows a simplified block dia - gram of the programmable universal dual phase-locked loop (pll). it provides accurate channel frequencies for cordless phone. the pll contains one 14-bit programmable counter, one phase detector, charge pump, un - lock detector and the 2nd local oscillator. the 12-bit programmable counter provides the ref - erence frequency for the receiver (rx) and transmitter (tx) loops. this dual pll is fully programmable through the c serial interface and supports most coun - try channel frequencies including usa, spain, australia, korea, new zealand, u.k., nether - lands, france, taiwan, and china. 5+ 4 ab 5+ 4 ab 5+ ! / & a b 5+ ! / & a b 1(
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application circuits HT9015 20 april 10, 2000 preliminary f f f $ % $ % f f f >c d 6 % $$$0 $6 % $ $6 c d $6 $6 % %0 ! $ $ 6> 6> $0 % $> $0 $$> $$$0 $$> $> $> $> $> % %$ % $ > $ $6 % $$$0 $ 8+* $6$ c d $ $ $> 6 $$$0 $ 6> $ $ $6 $ 6 c d % $ $$$$0 $ > $ $6 $ $$$$0 $ $$$$0 $6 > $> $$$$0 ! 2 !)) ( 2 !)) ( $> $> $> $ $$> !) !) 1 1 # ()) ! ! ) -)! ! ! ! ) .#
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china ct0 frequency base set channel number tx channel frequency (mhz) tx counter value (ref. freq.= 5.00khz f in r input frequency (mhz) (1st if= 10.7mhz) rx counter value (ref. freq.= 5.00khz) 1 45.250 9050 37.550 7510 2 45.275 9055 37.575 7515 3 45.300 9060 37.600 7520 4 45.325 9065 37.625 7525 5 45.350 9070 37.650 7530 6 45.375 9075 37.675 7535 7 45.400 9080 37.700 7540 8 45.425 9085 37.725 7545 9 45.450 9090 37.750 7550 10 45.475 9095 37.775 7555 hand set channel number tx channel frequency (mhz) tx counter value (ref. freq.= 5.00khz f in r input frequency (mhz) (1st if= 10.7mhz) rx counter value (ref. freq.= 5.00khz) 1 48.250 9650 34.550 6910 2 48.275 9655 34.575 6915 3 48.300 9660 34.600 6920 4 48.325 9665 34.625 6925 5 48.350 9670 34.650 6930 6 48.375 9675 34.675 6935 7 48.400 9680 34.700 6940 8 48.425 9685 34.725 6945 9 48.450 9690 34.750 6950 10 48.475 9695 34.775 6955 HT9015 21 april 10, 2000 preliminary
u.s.a. ct0 frequency (10 channels) base set channel number tx channel frequency (mhz) tx counter value (ref. freq.= 5.00khz f in r input frequency (mhz) (1st if= 10.695mhz) rx counter value (ref. freq. = 5.00khz) 1 46.610 9322 38.975 7795 2 46.630 9326 39.150 7830 3 46.670 9334 39.165 7833 4 46.710 9342 39.075 7815 5 46.730 9346 39.180 7836 6 46.770 9354 39.135 7827 7 46.830 9366 39.195 7839 8 46.870 9374 39.235 7847 9 46.930 9386 39.295 7859 10 46.970 9394 39.275 7855 hand set channel number tx channel frequency (mhz) tx counter value (ref. freq.= 5.00khz f in r input frequency (mhz) (1st if= 10.7mhz) rx counter value (ref. freq. = 5.00khz) 1 49.670 9934 35.915 7183 2 49.845 9969 35.935 7187 3 49.860 9972 35.975 7195 4 49.770 9954 36.015 7203 5 49.875 9975 36.035 7207 6 49.830 9966 36.075 7215 7 49.890 9978 36.135 7227 8 49.930 9986 36.175 7235 9 49.990 9998 36.235 7247 10 49.970 9994 36.275 7255 HT9015 22 april 10, 2000 preliminary
HT9015 23 april 10, 2000 preliminary copyright 2000 by holtek semiconductor inc. the information appearing in this data sheet is believed to be accurate at the time of publication. however, holtek assumes no responsibility arising from the use of the specifications described. the applications mentioned herein are used solely for the purpose of illustration and holtek makes no warranty or representation that such applications will be suitable without further modification, nor recommends the use of its products for application that may pres - ent a risk to human life due to malfunction or otherwise. holtek reserves the right to alter its products without prior notification. for the most up-to-date information, please visit our web site at http://www.holtek.com.tw. holtek semiconductor inc. (headquarters) no.3 creation rd. ii, science-based industrial park, hsinchu, taiwan, r.o.c. tel: 886-3-563-1999 fax: 886-3-563-1189 holtek semiconductor inc. (taipei office) 5f, no.576, sec.7 chung hsiao e. rd., taipei, taiwan, r.o.c. tel: 886-2-2782-9635 fax: 886-2-2782-9636 fax: 886-2-2782-7128 (international sales hotline) holtek semiconductor (hong kong) ltd. rm.711, tower 2, cheung sha wan plaza, 833 cheung sha wan rd., kowloon, hong kong tel: 852-2-745-8288 fax: 852-2-742-8657

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